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general description the aat1121 switchreg is a 1.5mhz step-down converter with an input voltage range of 2.7v to 5.5v and output as low as 0.6v. its low supply current, small size, and high switching frequency make the aat1121 the ideal choice for portable applications. the aat1121 delivers 250ma of load current, while maintaining a low 30a no load quiescent current. the 1.5mhz switching frequency minimizes the size of external components, while keeping switching losses low. the aat1121 feedback and control delivers excellent load regulation and transient response with a small output inductor and capacitor. the aat1121 is available in a pb-free, 8-pin, 2x2mm tdfn or stdfn package and is rated over the -40c to +85c temperature range. features ?v in range: 2.7v to 5.5v ?v out range: 0.6v to v in ? 250ma max output current ? up to 96% efficiency ? 30a typical quiescent current ? 1.5mhz switching frequency ? soft-start control ? over-temperature and current limit protection ? 100% duty cycle low-dropout operation ? <1a shutdown current ? small external components ? ultra-small tdfn22-8 or stdfn22-8 package ? temperature range: -40c to +85c applications ? bluetooth? headsets ? cellular phones ? digital cameras ? handheld instruments ? portable music players ? usb devices aat1121 1.5mhz, 250ma step-down converter typical application 1121.2007.03.1.2 1 switchreg ? 3.0 h l1 r 1 118k r 2 59k c 1 4.7f c 2 4.7f en fb vp vin lx pgnd gnd aat1121 v in v o = 1.8v 250m a
aat1121 1.5mhz, 250ma step-down converter 2 1121.2007.03.1.2 pin descriptions pin configuration tdfn22-8/stdfn22-8 (top view) pin # symbol function 1 vp input power pin; connected to the source of the p-channel mosfet. connect to the input capacitor. 2 vin input bias voltage for the converter. 3 gnd non-power signal ground pin. 4 fb feedback input pin. connect this pin to an external resistive divider for adjustable output. 5 n/c no connect. 6 en enable pin. a logic high enables normal operation. a logic low shuts down the converter. 7 lx switching node. connect the inductor to this pin. it is connected internally to the drain of both high- and low-side mosfets. 8 pgnd input power return pin; connected to the source of the n-channel mosfet. connect to the output and input capacitor return. ep exposed paddle (bottom): connect to ground directly beneath the package. gnd fb vp vin en n/c pgnd lx 3 4 1 2 6 5 8 7
aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 3 absolute maximum ratings 1 thermal information symbol description value units p d maximum power dissipation 2 w ja thermal resistance 2 50 c/w symbol description value units v in input voltage and bias power to gnd 6.0 v v lx lx to gnd -0.3 to v in + 0.3 v v out fb to gnd -0.3 to v in + 0.3 v v en en to gnd -0.3 to 6.0 v t j operating junction temperature range -40 to 150 c t lead maximum soldering temperature (at leads, 10 sec) 300 c 1. stresses above those listed in absolute maximum ratings may cause permanent damage to the device. functional operation at c ondi- tions other than the operating conditions specified is not implied. only one absolute maximum rating should be applied at any one time. 2. mounted on an fr4 board.
aat1121 1.5mhz, 250ma step-down converter 4 1121.2007.03.1.2 electrical characteristics 1 v in = 3.6v, t a = -40c to +85c, unless otherwise noted; typical values are t a = 25c. symbol description conditions min typ max units v in input voltage 2.7 5.5 v v in rising 2.6 v v uvlo uvlo threshold hysteresis 250 mv v in falling 2.0 v v out output voltage tolerance 2 i out = 0 to 250ma, -3.0 3.0 % v in = 2.7v to 5.5v v out output voltage range 0.6 v in v i q quiescent current no load 30 a i shdn shutdown current en = gnd 1.0 a i lim p-channel current limit 600 ma r ds(on)h high-side switch on resistance 0.59 r ds(on)l low-side switch on resistance 0.42 i lxleak lx leakage current v in = 5.5v, v lx = 0 to v in 1.0 a v linereg / v in line regulation v in = 2.7v to 5.5v 0.2 %/v v fb feedback threshold voltage accuracy v in = 3.6v 0.591 0.600 0.609 v i fb fb leakage current v out = 1.0v 0.2 a f osc oscillator frequency 1.5 mhz t s startup time from enable to output 100 s regulation t sd over-temperature shutdown threshold 140 c t hys over-temperature shutdown hysteresis 15 c v en(l) enable threshold low 0.6 v v en(h) enable threshold high 1.4 v i en input low current v in = v en = 5.5v -1.0 1.0 a 4 1121.2006.10.1.2 1. the aat1121 is guaranteed to meet performance specifications over the -40c to +85c operating temperature range and is assu red by design, characterization, and correlation with statistical process controls. 2. output voltage tolerance is independent of feedback resistor network accuracy.
typical characteristics aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 5 dc load regulation (v out = 3.0v; l = 4.7h) output current (ma) output error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 1000 v in = 5.0v v in = 4.2v v in = 3.6v efficiency vs. load (v out = 3.0v; l = 4.7h) output current (ma) efficiency (%) 40 50 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.6v v in = 4.2v v in = 5.0v dc load regulation (v out = 1.8v; l = 3.3h) output current (ma) output error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 1000 v in = 4.2v v in = 3.6v v in = 2.7v efficiency vs. load (v out = 1.8v; l = 3.3h) output current (ma) efficiency (%) 40 50 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.6v v in = 2.7v v in = 4.2v dc load regulation (v out = 1.2v; l = 1.5h) output current (ma) output error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 1000 v in = 3.6v v in = 4.2v v in = 2.7v efficiency vs. load (v out = 1.2v; l = 1.5h) output current (ma) efficiency (%) 30 40 50 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.6v v in = 2.7v v in = 5.0v v in = 4.2v
typical characteristics aat1121 1.5mhz, 250ma step-down converter 6 1121.2007.03.1.2 no load quiescent current vs. input voltage input voltage (v) supply current (a) 10 15 20 25 30 35 40 45 50 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 85 c 25 c -40 c frequency variation vs. input voltage input voltage (v) frequency variation (%) -4.0 -3.0 -2.0 -1.0 0.0 1.0 2.0 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 v out = 1.8v v out = 3.0v switching frequency variation vs. temperature (v in = 3.6v; v out = 1.8v) temperature ( c) variation (%) -10.0 -8.0 -6.0 -4.0 -2.0 0.0 2.0 4.0 6.0 8.0 10.0 -40 -20 0 20 40 60 80 100 output voltage error vs. temperature (v in = 3.6v; v out = 1.8v; i out = 250ma) temperature ( c) output error (%) -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 -40 -20 0 20 40 60 80 100 line regulation (v out = 1.8v) input voltage (v) accuracy (%) -0.3 -0.2 -0.1 0.0 0.1 0.2 0.3 0.4 0.5 0.6 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 i out = 250ma i out = 10ma i out = 0ma i out = 50ma i out = 150ma soft start (v in = 3.6v; v out = 1.8v; i out = 250ma; c ff = 100pf) enable and output voltage (top) (v) inductor current (bottom) (a) time (100s/div) 0.0 1.0 2.0 3.0 4.0 5.0 0.0 0.2 0.4 0.6 0.8 v en v o i l
typical characteristics aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 7 load transient response (10ma to 250ma; v in = 3.6v; v out = 1.8v; c out = 4.7f) output voltage (top) (v) load and inductor current (bottom) (200ma/div) time (25s/div) 1.6 1.7 1.8 1.9 2.0 -0.2 0.0 0.2 v o i lx i o 250ma 10ma load transient response (10ma to 250ma; v in = 3.6v; v out = 1.8v; c out = 4.7f; c ff = 100pf) output voltage (top) (v) load and inductor current (bottom) (200ma/div) time (25s/div) 1.6 1.7 1.8 -0.2 0.0 0.2 1.9 2.0 v o i lx i o 250ma 10ma n-channel r ds(on) vs. input voltage input voltage (v) r ds(on)l (m ) 300 350 400 450 500 550 600 650 700 750 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 120 c 100 c 85 c 25 c p-channel r ds(on) vs. input voltage input voltage (v) r ds(on)h (m ) 300 400 500 600 700 800 900 1000 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 120 c 100 c 85 c 25 c line response (v out = 1.8v @ 250ma; c ff = 100pf) output voltage (top) (v) input voltage (bottom) (v) time (25s/div) 1.70 1.75 1.80 1.85 1.90 3.0 3.5 4.0 4.5 5.0 v o v in
typical characteristics aat1121 1.5mhz, 250ma step-down converter 8 1121.2007.03.1.2 output ripple (v in = 3.6v; v out = 1.8v; i out = 1ma) output voltage (ac coupled) (top) (mv) inductor current (bottom) (a) time (2s/div) -20 0 20 40 -0.01 0.00 0.01 0.02 0.03 0.04 v o i l output ripple (v in = 3.6v; v out = 1.8v; i out = 250ma) output voltage (ac coupled) (top) (mv) inductor current (bottom) (a) time (200ns/div) -20 0 20 40 0.0 0.1 0.2 0.3 v o i l
aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 9 functional description the aat1121 is a high performance 250ma, 1.5mhz monolithic step-down converter designed to operate with an input voltage range of 2.7v to 5.5v. the converter operates at 1.5mhz, which minimizes the size of external components. typical values are 3.3h for the output inductor and 4.7f for the ceramic output capacitor. the device is designed to operate with an output voltage as low as 0.6v. power devices are sized for 250ma current capability while maintaining over 90% efficiency at full load. light load efficiency is maintained at greater than 80% down to 1ma of load current. at dropout, the converter duty cycle increases to 100% and the output voltage tracks the input volt- age minus the r ds(on) drop of the p-channel high- side mosfet. a high-dc gain error amplifier with internal com- pensation controls the output. it provides excellent transient response and load/line regulation. soft start eliminates any output voltage overshoot when the enable or the input voltage is applied. functional block diagram en lx err amp logic dh dl pgnd vp fb gnd voltage reference input vin
aat1121 1.5mhz, 250ma step-down converter 10 1121.2007.03.1.2 control loop the aat1121 is a 250ma current mode step-down converter. the current through the p-channel mosfet (high side) is sensed for current loop control, as well as short-circuit and overload pro- tection. a fixed slope compensation signal is added to the sensed current to maintain stability for duty cycles greater than 50%. the peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. the output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. internal loop compen- sation terminates the transconductance voltage error amplifier output. the error amplifier reference is fixed at 0.6v. soft start / enable soft start increases the inductor current limit point in discrete steps when the input voltage or enable input is applied. it limits the current surge seen at the input and eliminates output voltage overshoot. when pulled low, the enable input forces the aat1121 into a low-power, non-switching state. the total input current during shutdown is less than 1a. current limit and over-temperature protection for overload conditions, the peak input current is lim- ited. as load impedance decreases and the output voltage falls closer to zero, more power is dissipated internally, raising the device temperature. thermal protection completely disables switching when inter- nal dissipation becomes excessive, protecting the device from damage. the junction over-temperature threshold is 140c with 15c of hysteresis. under-voltage lockout internal bias of all circuits is controlled via the v in power. under-voltage lockout (uvlo) guarantees sufficient v in bias and proper operation of all inter- nal circuits prior to activation. applications information inductor selection the step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. the output induc- tor value must be selected so the inductor current down slope meets the internal slope compensation requirements. the internal slope compensation for the adjustable and low-voltage fixed versions of the aat1121 is 0.45a/sec. this equates to a slope compensation that is 75% of the inductor current down slope for a 1.8v output and 3.0h inductor. this is the internal slope compensation for the aat1121. when externally programming to 3.0v, the calculated inductance is 5.0h. in this case, a standard 4.7h value is selected. for most designs, the aat1121 operates with an inductor value of 1h to 4.7h. table 1 displays inductor values for the aat1121 with different output voltage options. manufacturer's specifications list both the inductor dc current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. the inductor should not show any appreciable saturation under normal load conditions. some inductors may meet the peak and average current ratings yet result in excessive loss- es due to a high dcr. always consider the losses associated with the dcr and its effect on the total converter efficiency when selecting an inductor. 10 1121.2007.03.1.2 0.75 ? v o l = = 1.67 ? v o = 1.67 ? 3.0v = 5.0h m 0.75 ? v o 0.45a sec a sec a a sec 0.75 ? v o m = = = 0.45 l 0.75 ? 1.8v 3.0h a sec
table 1: inductor values. the 3.0h cdrh2d09 series inductor selected from sumida has a 150m dcr and a 470ma dc current rating. at full load, the inductor dc loss is 9.375mw which gives a 2.08% loss in efficiency for a 250ma, 1.8v output. input capacitor select a 4.7f to 10f x7r or x5r ceramic capac- itor for the input. to estimate the required input capacitor size, determine the acceptable input rip- ple level (v pp ) and solve for c in . the calculated value varies with input voltage and is a maximum when v in is double the output voltage. always examine the ceramic capacitor dc voltage coefficient characteristics when selecting the prop- er value. for example, the capacitance of a 10f, 6.3v, x5r ceramic capacitor with 5.0v dc applied is actually about 6f. the maximum input capacitor rms current is: the input capacitor rms ripple current varies with the input and output voltage and will always be less than or equal to half of the total dc load current. for v in = 2 x v o the term appears in both the input voltage ripple and input capacitor rms current equations and is a maximum when v o is twice v in . this is why the input voltage ripple and the input capacitor rms current ripple are a maximum at 50% duty cycle. the input capacitor provides a low impedance loop for the edges of pulsed current drawn by the aat1121. low esr/esl x7r and x5r ceramic capacitors are ideal for this function. to minimize stray inductance, the capacitor should be placed as closely as possible to the ic. this keeps the high frequency content of the input current localized, minimizing emi and input voltage ripple. the proper placement of the input capacitor (c1) can be seen in the evaluation board layout in figure 2. a laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. the induc- tance of these wires, along with the low-esr ceramic input capacitor, can create a high q net- work that may affect converter performance. this problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. errors in the loop phase and gain meas- urements can also result. since the inductance of a short pcb trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. output voltage (v) l1 (h) 1.0 1.5 1.2 2.2 1.5 2.7 1.8 3.0 2.5 3.9 3.0 4.7 3.3 5.6 aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 11 ?? 1 - ?? v o v in v o v in i o rms(max) i 2 = ?? 1 - = d (1 - d) = 0.5 2 = ?? v o v in v o v in 1 2 ?? i rms = i o 1 - ?? v o v in v o v in c in(min) = 1 ?? - esr 4 f s ?? v pp i o ?? 1 - = for v in = 2 v o ?? v o v in v o v in 1 4 ?? 1 - ?? v o v in c in = v o v in ?? - esr f s ?? v pp i o
in applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high esr tantalum or aluminum electrolytic should be placed in parallel with the low esr, esl bypass ceramic. this dampens the high q network and stabilizes the system. output capacitor the output capacitor limits the output ripple and provides holdup during large load transitions. a 4.7f to 10f x5r or x7r ceramic capacitor typi- cally provides sufficient bulk capacitance to stabi- lize the output during large load transitions and has the esr and esl characteristics necessary for low output ripple. for enhanced transient response and low temperature operation application, a 10f (x5r, x7r) ceramic capacitor is recommended to stabilize extreme pulsed load conditions. the output voltage droop due to a load transient is dominated by the capacitance of the ceramic out- put capacitor. during a step increase in load cur- rent, the ceramic output capacitor alone supplies the load current until the loop responds. within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. the relationship of the output volt- age droop during the three switching cycles to the output capacitance can be estimated by: once the average inductor current increases to the dc load level, the output voltage recovers. the above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. the internal voltage loop compensation also limits the minimum output capacitor value to 4.7f. this is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. increased output capacitance will reduce the crossover frequency with greater phase margin. the maximum output capacitor rms ripple current is given by: dissipation due to the rms current in the ceramic output capacitor esr is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. adjustable output resistor selection resistors r1 and r2 of figure 1 program the output to regulate at a voltage higher than 0.6v. to limit the bias current required for the external feedback resis- tor string while maintaining good noise immunity, the suggested value for r2 is 59k . decreased resistor values are necessary to maintain noise immunity on the fb pin, resulting in increased quiescent current. table 2 summarizes the resistor values for various output voltages. with enhanced transient response for extreme pulsed load application, an external feed-forward capacitor, (c3 in figure 1), can be added. table 2: adjustable resistor values for step-down converter. r2 = 59k r2 = 221k v out (v) r1 (k ) r1 (k ) 0.8 19.6 75 0.9 29.4 113 1.0 39.2 150 1.1 49.9 187 1.2 59.0 221 1.3 68.1 261 1.4 78.7 301 1.5 88.7 332 1.8 118 442 1.85 124 464 2.0 137 523 2.5 187 715 3.3 267 1000 aat1121 1.5mhz, 250ma step-down converter 12 1121.2007.03.1.2 12 1121.2007.03.1.2 ?? ?? r1 = -1 r2 = - 1 59k = 267k v out v ref ?? ?? 3.3v 0.6v 1 23 v out (v in(max) - v out ) rms(max) i l f v in(max) = c out = 3 i load v droop f s
aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 13 thermal calculations there are three types of losses associated with the aat1121 step-down converter: switching loss- es, conduction losses, and quiescent current loss- es. conduction losses are associated with the r ds(on) characteristics of the power output switch- ing devices. switching losses are dominated by the gate charge of the power output switching devices. at full load, assuming continuous conduc- tion mode (ccm), a simplified form of the losses is given by: i q is the step-down converter quiescent current. the term t sw is used to estimate the full load step- down converter switching losses. for the condition where the step-down converter is in dropout at 100% duty cycle, the total device dis- sipation reduces to: since r ds(on) , quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. given the total losses, the maximum junction tem- perature can be derived from the ja for the tdfn22-8 package which is 50c/w. figure 1: aat1121 schematic. t j(max) = p total ja + t amb p total = i o 2 r dson(h) + i q v in p total i o 2 (r dson(h) v o + r dson(l) [v in - v o ]) v in = + (t sw f i o + i q ) v in r1 adj. r2 59k l1 4.7f c2 4.7f c1 vp 1 gnd 3 n/c 5 en 6 lx 7 pgnd 8 vin 2 fb 4 aat1121 u1 vin gnd +vout gnd c3 (optional) 100pf lx
layout the suggested pcb layout for the aat1121 is shown in figures 2, 3, and 4. the following guide- lines should be used to help ensure a proper layout. 1. the input capacitor (c1) should connect as closely as possible to vp (pin 1), pgnd (pin 8), and gnd (pin 3) 2. c2 and l1 should be connected as closely as possible. the connection of l1 to the lx pin should be as short as possible. do not make the node small by using narrow trace. the trace should be kept wide, direct and short. 3. the feedback pin (pin 4) should be separate from any power trace and connect as closely as possible to the load point. sensing along a high-current load trace will degrade dc load regulation. feedback resistors should be placed as closely as possible to the fb pin (pin 4) to minimize the length of the high imped- ance feedback trace. if possible, they should also be placed away from the lx (switching node) and inductor to improve noise immunity. 4. the resistance of the trace from the load return to pgnd (pin 8) and gnd (pin 3) should be kept to a minimum. this will help to minimize any error in dc regulation due to differences in the potential of the internal signal ground and the power ground. 5. a high density, small footprint layout can be achieved using an inexpensive, miniature, non- shielded, high dcr inductor. aat1121 1.5mhz, 250ma step-down converter 14 1121.2007.03.1.2 figure 2: aat1121 evaluation board figure 3: exploded view of aat1121 top side layout. evaluation board top side layout. figure 4: aat1121 evaluation board bottom side layout.
step-down converter design example specifications v o = 1.8v @ 250ma, pulsed load i load = 200ma v in = 2.7v to 4.2v (3.6v nominal) f s = 1.5mhz t amb = 85c 1.8v output inductor (use 3.0h; see table 1) for sumida inductor cdrh2d09-3r0, 3.0h, dcr = 150m . 1.8v output capacitor v droop = 0.1v aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 15 1 23 1 1.8v (4.2v - 1.8v) 3.0h 1.5mhz 4.2v 23 rms i l1 f s v in(max) = 3 i load v droop f s 3 0.2a 0.1v 1.5mhz c out = = = 4f (use 4.7f) = 66marms (v o ) (v in(max) - v o ) = p esr = esr i rms 2 = 5m (66ma) 2 = 21.8w v o v o 1.8 v 1.8v i l1 = ? 1 - = ? 1 - = 228m a l1 ? f v in 3.0h ? 1.5mhz 4.2v i pkl1 = i o + i l1 = 250ma + 114ma = 364ma 2 p l1 = i o 2 ? dcr = 250ma 2 ? 150m = 9.375mw ? ? ? ? ? ? ? ? l1 = 1.67 ? v o2 = 1.67 ? 1.8v = 3h sec a sec a
input capacitor input ripple v pp = 25mv aat1121 losses aat1121 1.5mhz, 250ma step-down converter 16 1121.2007.03.1.2 t j(max) = t amb + ja p loss = 85 c + (50 c/w) 26.14mw = 86.3 c p total + (t sw f i o + i q ) v in i o 2 (r dson(hs) v o + r dson(ls) [v in -v o ] ) v in = = + (5ns 1.5mhz 0.2a + 30a) 4.2v = 26.14mw 0.2 2 (0.59 1.8v + 0.42 [4.2v - 1.8v]) 4.2v i o rms i p = esr i rms 2 = 5m (0.1a) 2 = 0.05mw 2 = = 0.1arms c in = = = 1.38f (use 4.7f ) 1 ?? - esr 4 f s ?? v pp i o 1 ?? - 5m 4 1.5mhz ?? 25mv 0.2a
table 3: evaluation board component values. table 4: suggested inductors and suppliers. inductance max dc dcr size (mm) manufacturer part number (h) current (ma) (m ) lxwxh type sumida cdrh2d09-1r5 1.5 730 88 3.0x3.0x1.0 shielded sumida cdrh2d09-2r2 2.2 600 115 3.0x3.0x1.0 shielded sumida cdrh2d09-2r5 2.5 530 135 3.0x3.0x1.0 shielded sumida cdrh2d09-3r0 3 470 150 3.0x3.0x1.0 shielded sumida cdrh2d09-3r9 3.9 450 180 3.0x3.0x1.0 shielded sumida cdrh2d09-4r7 4.7 410 230 3.0x3.0x1.0 shielded sumida cdrh2d09-5r6 5.6 370 260 3.0x3.0x1.0 shielded sumida cdrh2d11-1r5 1.5 900 54 3.2x3.2x1.2 shielded sumida cdrh2d11-2r2 2.2 780 78 3.2x3.2x1.2 shielded sumida cdrh2d11-3r3 3.3 600 98 3.2x3.2x1.2 shielded sumida cdrh2d11-4r7 4.7 500 135 3.2x3.2x1.2 shielded taiyo yuden nr3010 1.5 1200 80 3.0x3.0x1.0 shielded taiyo yuden nr3010 2.2 1100 95 3.0x3.0x1.0 shielded taiyo yuden nr3010 3.3 870 140 3.0x3.0x1.0 shielded taiyo yuden nr3010 4.7 750 190 3.0x3.0x1.0 shielded fdk mipwt3226d-1r5 1.5 1200 90 3.2x2.6x0.8 chip shielded fdk mipwt3226d-2r2 2.2 1100 100 3.2x2.6x0.8 chip shielded fdk mipwt3226d-3r0 3 1000 120 3.2x2.6x0.8 chip shielded fdk mipwt3226d-4r2 4.2 900 140 3.2x2.6x0.8 chip shielded output voltage r2 = 59k r2 = 221k 1 v out (v) r1 (k ) r1 (k ) l1 (h) 0.6 2 1.5 0.8 19.6 75 1.5 0.9 29.4 113 1.5 1.0 39.2 150 1.5 1.1 49.9 187 1.5 1.2 59.0 221 1.5 1.3 68.1 261 1.5 1.4 78.7 301 2.2 1.5 88.7 332 2.7 1.8 118 442 3.0/3.3 1.85 124 464 3.0/3.3 2.0 137 523 3.0/3.3 2.5 187 715 3.9/4.2 3.3 267 1000 5.6 aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 17 1. for reduced quiescent current, r2 = 221k . 2. r2 is opened, r1 is shorted.
table 5: surface mount capacitors. value voltage temp. case manufacturer part number (f) rating co. size murata grm118r60j475ke19b 4.7 6.3 x5r 0603 murata grm188r60j106me47d 10 6.3 x5r 0603 aat1121 1.5mhz, 250ma step-down converter 18 1121.2007.03.1.2
ordering information package information 3 tdfn22-8 all dimensions in millimeters. output voltage package marking 1 part number (tape and reel) 2 0.6v tdfn22-8 rwxyy aat1121ips-0.6-t1 0.6v stdfn22-8 rwxyy aat1121ies-0.6-t1 aat1121 1.5mhz, 250ma step-down converter 1121.2007.03.1.2 19 1. xyy = assembly and date code. 2. sample stock is generally held on all part numbers listed in bold . 3. the leadless package family, which includes qfn, tqfn, dfn, tdfn and stdfn, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. a solder fillet at the exposed copper edge cannot be guaranteed and is not re quired to ensure a proper bottom solder connection. 2.000 all analogictech products are offered in pb-free packaging. the term pb-free means semiconductor products that are in compliance with current rohs standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. for more information, please visit our website at http://www.analogictech.com/pbfree.
stdfn22-8 all dimensions in millimeters. aat1121 1.5mhz, 250ma step-down converter 20 1121.2007.03.1.2 advanced analogic technologies, inc. 830 e. arques avenue, sunnyvale, ca 94085 phone (408) 737- 4600 fax (408) 737- 4611 ? advanced analogic technologies, inc. analogictech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an analogictech pr oduct. no circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. analogictech reserves the right to make changes to their products or specifications or to discontinue any product or service with- out notice. except as provided in analogictechs terms and conditions of sale, analogictech assumes no liability whatsoever, an d analogictech disclaims any express or implied war- ranty relating to the sale and/or use of analogictech products including liability or warranties relating to fitness for a part icular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. in order to minimize risks associated with the customers applications, adequa te design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. testing and other quality control techniques are utilized to the extent an alogictech deems necessary to support this warranty. specific testing of all parameters of each device is not necessarily performed. analogictech and the analogictech logo are trad emarks of advanced analogic technologies incorporated. all other brand and product names appearing in this document are registered trademarks or trademarks of their respective holder s. 2.00

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